Key research themes
1. How can adaptive delta modulation be optimized for Laplacian-distributed signals and nonuniform sampling to improve coding efficiency and bit error robustness?
This research area explores enhancements to traditional delta modulation (DM) techniques by introducing adaptive elements such as variable quantization levels (e.g., three-level quantization), step size adaptation, and nonuniform sampling rates tailored for signals exhibiting Laplacian statistics typical in speech and other nonstationary signals. This theme is crucial as it balances compression efficiency, signal reconstruction quality, and robustness to channel errors, which are prominent in real-time and low-power communications.
2. What are the benefits and considerations of using triangular QAM constellations for adaptive modulation in fading and noise environments?
This theme focuses on studying non-square signal constellations, specifically triangular quadrature amplitude modulation (TQAM), to improve power and spectral efficiency in adaptive modulation schemes. It considers modulation orders beyond powers-of-two, detection complexity trade-offs, and robust symbol mapping strategies, comparing TQAM variants over AWGN and Rayleigh fading channels. Insights here are important for designing adaptive wireless systems optimizing both spectral efficiency and receiver complexity.
3. How can statistical and signal processing methods improve the power allocation, stability, and detection in adaptive wireless communication systems involving modulation variants and delta modulators?
This research area entails advanced system-level approaches for enhancing wireless communication robustness and efficiency, combining power allocation strategies in differential distributed space-time coding, stability and chaos analysis of sigma-delta modulators, and cyclostationary detection techniques for cognitive radio modulations such as GFDM. These methods address challenges in channel fading, interference, quantization nonlinearities, and spectrum scarcity critical for next-generation wireless systems.
![The superposition of these three waveforms presented in Fig.4 gives the final model of the switch [24]. where a@ is the damping coefficient. The envelope of the ringing effect is given below. The approximate switching behavior of IGBT is shown in Fig.4.](https://smart.socialdev.workers.dev/page-https-figures.academia-assets.com/110408812/figure_004.jpg)


![FIGURE 10. Leakage current measurement for three-phase four-wire systems [37].](https://smart.socialdev.workers.dev/page-https-figures.academia-assets.com/110408812/figure_010.jpg)






























![Fig. 13. Comparison of simulated and measured IL. (a) CM. (b) DM. considered. The passivity of a component requires that the component be dissipative in energy. However, the IRFA method cannot guarantee the passivity of the calculated rational function. During the past ten years, many works have been reported on the passivity verification and enforcement techniques [24], [25]. In this paper, all the extracted results are verified to be passive using the method of [24]. In practice, as CM chokes are naturally dissipative in HF due to core losses and copper losses, the passivity is usually respected if fitting precision is good enough.](https://smart.socialdev.workers.dev/page-https-figures.academia-assets.com/108384582/figure_012.jpg)




![Fig. 2. HF circuit model for CM chokes proposed in [15]. (a) Toroidal CM choke. (b) HF equivalent circuit. (c) Equivalent circuit of leakage impedance Z,. (d) Equivalent circuit of magnetizing impedance Z). of the HF model is chosen heuristically, which requires lots of experience and tests. Moreover, the extraction procedure derives the parameters of the model by observing the impedance curves, leading to quite time-consuming trial/error iterations.](https://smart.socialdev.workers.dev/page-https-figures.academia-assets.com/108384582/figure_002.jpg)



![Fig. 3. Impedance measurement configurations for the extraction. (a) To. (b) Ti. (c) To. (d) Ts. (e) Ta. resistance, the leakage inductance and their variations due to skin and proximity effects of the winding conductor [see Fig. 2(c)]. The magnetizing impedance Z, describes the behavior of magnetic core, including the frequency-dependent inductance and losses [see Fig. 2(d)]. In addition, C, stands for the self-parasitic capacitance of each winding whereas the sum C,+C,+C, is related to the inter-winding capacitances of the component. Examining the admittance Y) = (Z)', it is found that Y, contains: 1) One pole at origin: the branch of L>;](https://smart.socialdev.workers.dev/page-https-figures.academia-assets.com/108384582/figure_003.jpg)
![Fig. 1. Typical topology of EMI filter specific to limited applications [5], [6]. Modeling methods based on measurements are more general, direct and accurate for describing the characteristics of the device under study. Wenhua Tan, Carlos Cuellar, Member, IEEE, Xavier Margueron, Member, IEEE, and Nadir Idir, Member, IEEE The insertion loss (IL) of an EMI filter is usually measured with 50Q/50Q convention. However, the IL of the filter under working condition depends on the impedances of the source and the load, which vary with frequency [7], [8]. In order to obtain the IL of the filter, many solutions have been reported. In [9], a four-port measurement method using vector network analyzer is presented. This method consists in a black-box modeling of the whole filter with mixed-mode S-parameters. By post-processing the obtained S-parameter data, the IL of the filter can hence be calculated with any source and load impedances. In [10], a modal model of common mode (CM) chokes based on four-port S-parameter measurements is presented. Though modal models enable to analyze the conversion of the noise between differential mode (DM) and CM, they also require compatible modal model of noise sources for simulations, which complicates the modeling process. An alternative is to use equivalent circuit models, which are physic based and are compatible with most of the simulation tools. In [11], the equivalent circuit of a DM EMI filter is identified by S-parameters measurements. This approach can correctly extract the parasitic couplings in the filter, resulting in good modeling precision. Impedance measurement is a more frequently used technique which has ong been studied for identifying the equivalent circuits of passive magnetic components [12], [13]. Recently, a lumped- element high frequency (HF) model for CM chokes has been proposed [14], [15]. This model can be easily built by extracting the parameters from impedance measurement results and can effectively describe the HF characteristics of the studied CM choke and EMI filter. However, the topology A High Frequency Equivalent Circuit and Parameter Extraction Procedure for Common Mode Choke in EMI Filter](https://smart.socialdev.workers.dev/page-https-figures.academia-assets.com/108384582/figure_001.jpg)








![FIGURE 4. Visualization of the synthetic data: the power of used SMCs, DMC and AWGN is illustrated in log-scale (dB) for (a) a LOS case at agent position p = [6, 6]" and (b) a non-LOS case at agent position p =[3.7, 1.8]". Two reference AWGN levels are shown using (39) with the given sNR(™) values. The respective SNR" values obtained using (40) are (a) SNR = 20 dB / 40 dB; and (b) SNR" = 9 dB / 29 dB.](https://smart.socialdev.workers.dev/page-https-figures.academia-assets.com/105473279/figure_004.jpg)



![TABLE 1. |bm(¢,)|2 SINR, in dB of the respective SMCs and the four used antennas (cf. Fig. 12) obtained using (20) with the estimated amplitudes from (48). The column added contains the sum over all antennas, whereas the entry omni contains the results from [32] using an omni-directional antenna in the same setup. where we use the amplitude estimates obtained by (48). As seen in (38), these quantities indicate the quality of SMCs and highlight how each antenna can be used to focus on par- ticular SMCs from different directions. E.g., we see that the SMC from the plasterboard east wall achieves a high SINR value from the east antenna measurement. For comparison, we include a sum of the weighted SINRs (similar to what is used in (38) to quantify the total information collected from each SMC with the multi-antenna system), as well as the SINRs of SMCs using a single omni-directional antenna at the anchor from [32] (the latter were obtained by method- of-moments estimation). The information gain of specific directional antennas is highlighted and the overall higher performance is justified. A variant of the AWGN-based algo- rithm was implemented on low-cost devices based on the DecaWave DWM1000 module as described in [31]. The sys- tem was evaluated in a field test and put in context with other indoor localization systems in terms of accuracy and required infrastructure.](https://smart.socialdev.workers.dev/page-https-figures.academia-assets.com/105473279/table_001.jpg)













![Equation (5) shows that the 3"! order harmonic component is completely removed for proposed one-third (m=3) conversion of 50 Hz frequency. From the point of view of power quality, the proposed cycloconverter is much better than conventional cycloconverter due to its lower THD. Thus for all order frequency conversion, the Fourier series expression of output waveform can be calculated using the half-cycle pair method according to conventional half-cycle pair formula of [12]. Fig. 7. Output voltage for one-third (m=3) of 50 Hz conversion of proposed cycloconverter.](https://smart.socialdev.workers.dev/page-https-figures.academia-assets.com/103685555/figure_007.jpg)






